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參數(shù)資料
| 型號： | LM2635MX/NOPB |
| 廠商： | NATIONAL SEMICONDUCTOR CORP |
| 元件分類： | 穩(wěn)壓器 |
| 英文描述： | SWITCHING CONTROLLER, 350 kHz SWITCHING FREQ-MAX, PDSO20 |
| 封裝： | PLASTIC, SO-20 |
| 文件頁數(shù)： | 13/13頁 |
| 文件大?。?/td> | 290K |
| 代理商： | LM2635MX/NOPB |
Applications Information (Continued)
The control-to-output transfer function is
The ESR zero frequency is:
The power stage double pole frequency is:
The corresponding Bode plots are shown in
Figure 5.
Since the ESR zero frequency is so low, it effectively cancels
the phase shift from one of the power stage poles. This limits
the total phase shift to 90%.
Although this regulator design is stable (phase shift is <90
when gain = 0dB), it needs compensation to improve the DC
gain and cut off frequency (0dB frequency). Otherwise, the
low DC gain may cause a poor line regulation, and the low
cutoff frequency will hurt transient response performance.
The transfer function for the 2-pole-1-zero compensation
network shown in
Figure 4 is:
where
One of the poles is located at origin to help achieve the high-
est DC gain. So there are three parameters to determine, the
position of the zero, the position of the second pole, and the
constant A. To determine the cutoff frequency and phase
margin, the loop bode plots need to be generated. The loop
transfer function is:
TF = TF1 x TF2
By choosing the zero close to the double pole position and
the second pole to half of the switching frequency, the closed
loop transfer function turns out to be very good.
That is, if f
Z = 1.32 kHz, fP = 153 kHz, and A = 4.8 x 10
6
F,
then the cutoff frequency will be 50 kHz, the phase margin
will be 72, and the DC gain will be that of the error amplifier.
See
Figure 6 below.
The compensation network component values can be deter-
mined by the following equations:
Notice there are three equations but four variables. So one
of the variables can be chosen arbitrarily. Since the current
driving capability of the error amplifier is limited to around
3 mA, it is a good idea to have a high impedance path from
the output of the error amplifier to the output of the converter.
From the above equations it can be told that a larger R
2 will
DS100119-13
FIGURE 5. Control-to-Output Bode Plots
DS100119-17
FIGURE 6. Loop Bode Plots
www.national.com
9
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