參數(shù)資料
    型號: ISL6524CB
    廠商: INTERSIL CORP
    元件分類: 穩(wěn)壓器
    英文描述: Adjustable Precision Shunt Regulator 5-SOT-23 -40 to 125
    中文描述: SWITCHING CONTROLLER, 215 kHz SWITCHING FREQ-MAX, PDSO28
    封裝: PLASTIC, MS-013-AE, SOIC-28
    文件頁數(shù): 12/16頁
    文件大?。?/td> 445K
    代理商: ISL6524CB
    12
    FN9015.3
    April 18, 2005
    Compensation Break Frequency Equations
    Figure 12 shows an asymptotic plot of the DC-DC converter’s
    gain vs. frequency. The actual Modulator Gain has a high gain
    peak dependent on the quality factor (Q) of the output filter,
    which is not shown in Figure 12. Using the above guidelines
    should yield a Compensation Gain similar to the curve plotted.
    The open loop error amplifier gain bounds the compensation
    gain. Check the compensation gain at F
    P2
    with the capabilities
    of the error amplifier. The Closed Loop Gain is constructed on
    the log-log graph of Figure 12 by adding the Modulator Gain (in
    dB) to the Compensation Gain (in dB). This is equivalent to
    multiplying the modulator transfer function to the compensation
    transfer function and plotting the gain.
    The compensation gain uses external impedance networks
    Z
    FB
    and Z
    IN
    to provide a stable, high bandwidth (BW) overall
    loop. A stable control loop has a gain crossing with
    -20dB/decade slope and a phase margin greater than
    45 degrees. Include worst case component variations when
    determining phase margin.
    Component Selection Guidelines
    Output Capacitor Selection
    The output capacitors for each output have unique
    requirements. In general the output capacitors should be
    selected to meet the dynamic regulation requirements.
    Additionally, the PWM converter requires an output capacitor
    to filter the current ripple. The load transient for the
    microprocessor core requires high quality capacitors to
    supply the high slew rate (di/dt) current demands.
    PWM Output Capacitors
    Modern microprocessors produce transient load rates
    above 1A/ns. High frequency capacitors initially supply the
    transient current and slow the load rate-of-change seen by
    the bulk capacitors. The bulk filter capacitor values are
    generally determined by the ESR (effective series
    resistance) and voltage rating requirements rather than
    actual capacitance requirements.
    High frequency decoupling capacitors should be placed as
    careful not to add inductance in the circuit board wiring that
    could cancel the usefulness of these low inductance
    components. Consult with the manufacturer of the load on
    specific decoupling requirements.
    Use only specialized low-ESR capacitors intended for
    switching-regulator applications for the bulk capacitors. The
    bulk capacitor’s ESR determines the output ripple voltage and
    the initial voltage drop following a high slew-rate transient’s
    edge. An aluminum electrolytic capacitor’s ESR value is
    related to the case size with lower ESR available in larger
    case sizes. However, the equivalent series inductance (ESL)
    of these capacitors increases with case size and can reduce
    the usefulness of the capacitor to high slew-rate transient
    loading. Unfortunately, ESL is not a specified parameter. Work
    with your capacitor supplier and measure the capacitor’s
    impedance with frequency to select a suitable component. In
    most cases, multiple electrolytic capacitors of small case size
    perform better than a single large case capacitor.
    Linear Output Capacitors
    The output capacitors for the linear regulators provide
    dynamic load current. Thus capacitors C
    OUT2
    , C
    OUT3
    , and
    C
    OUT4
    should be selected for transient load regulation.
    PWM Output Inductor Selection
    The PWM converter requires an output inductor. The output
    inductor is selected to meet the output voltage ripple
    requirements and sets the converter’s response time to a
    load transient. The inductor value determines the converter’s
    ripple current and the ripple voltage is a function of the ripple
    current. The ripple voltage and current are approximated by
    the following equations:
    Increasing the value of inductance reduces the ripple
    current and voltage. However, large inductance values
    increase the converter’s response time to a load transient.
    One of the parameters limiting the converter’s response to
    a load transient is the time required to change the inductor
    current. Given a sufficiently fast control loop design, the
    ISL6524 will provide either 0% or 100% duty cycle in
    response to a load transient. The response time is the time
    interval required to slew the inductor current from an initial
    F
    Z1
    -----------------------------------
    =
    F
    Z2
    +
    2
    R1
    R3
    C3
    ------------------------------------------------------
    =
    F
    P1
    2
    π
    R
    2
    C1
    C2
    +
    ----------------------
    ×
    ×
    ------------------------------------------------------
    =
    F
    P2
    2
    R
    3
    C3
    -----------------------------------
    =
    100
    80
    60
    40
    20
    0
    -20
    -40
    -60
    F
    P1
    F
    Z2
    10M
    1M
    100K
    10K
    1K
    100
    10
    OPEN LOOP
    ERROR AMP GAIN
    F
    Z1
    F
    P2
    F
    LC
    F
    ESR
    COMPENSATION
    GAIN
    G
    FREQUENCY (Hz)
    MODULATOR
    GAIN
    FIGURE 12. ASYMPTOTIC BODE PLOT OF CONVERTER GAIN
    CLOSED LOOP
    GAIN
    20
    P
    VP
    log
    20
    R1
    log
    I
    V
    -------------------------------
    V
    S
    V
    IN
    ---------------
    ×
    =
    V
    OUT
    I
    ESR
    ×
    =
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