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| 型號： | IRU3038 |
| 廠商： | International Rectifier |
| 英文描述： | RES CHIP 383OHM 1/10 1% 100PP |
| 中文描述： | 同步PWM控制器終止電源應(yīng)用 |
| 文件頁數(shù)： | 9/18頁 |
| 文件大?。?/td> | 139K |
| 代理商： | IRU3038 |
IRU3038
9
Rev. 2.0
09/12/02
www.irf.com
For a general solution for unconditionally stability for
ceramic capacitor with very low ESR and any type of
output capacitors, in a wide range of ESR values we
should implement local feedback with a compensation
network. The typically used compensation network for
voltage-mode controller is shown in Figure 7.
Figure 7 - Compensation network with local
feedback and its asymptotic gain plot.
In such configuration, the transfer function is given by:
1 -
g
m
Z
f
1 +
g
m
Z
IN
The error amplifier gain is independent of the transcon-
ductance under the following condition:
g
m
Z
f
>> 1 and
g
m
Z
IN
>>1 ---(14)
By replacing Z
IN
and Z
f
according to Figure 7, the trans-
former function can be expressed as:
As known, transconductance amplifier has high imped-
ance (current source) output, therefore, consider should
be taken when loading the E/A output. It may exceed its
source/sink output current capability, so that the ampli-
fier will not be able to swing its output voltage over the
necessary range.
The compensation network has three poles and two ze-
ros and they are expressed as follows:
V
e
V
OUT
=
Cross Over Frequency:
The stability requirement will be satisfied by placing the
poles and zeros of the compensation network according
to following design rules. The consideration has been
taken to satisfy condition (14) regarding transconduc-
tance error amplifier.
1)
Select the crossover frequency:
Fo < F
ESR
and Fo
≤
(1/10 ~ 1/6)
×
f
S
2)
Select R
7
, so that R
7
>>
3)
Place first zero before LC’s resonant frequency pole.
F
Z1
75% F
LC
1
2
π ×
F
Z1
×
R
7
4)
Place third pole at the half of the switching frequency.
F
P3
=f
S
2
1
2
π ×
R
7
×
F
P3
C
12
> 50pF
If not, change R
7
selection.
5)
Place R
7
in equation (15) and calculate C
10
:
2
g
m
C
11
=
F
P1
= 0
1
π×
C
10
×
(R
6
+ R
8
)
F
Z2
= 2
1
2
π×
C
10
×
R
6
F
Z1
=
1
2
π×
R
7
×
C
11
F
P3
=
2
π×
R
7
×
1
1
2
π×
R
7
×
C
12
F
P2
=
1
2
π×
R
8
×
C
10
C
12
+C
11
C
12
×
C
11
V
OUT
Vp=V
REF
R
5
R
6
R
8
C
10
C
12
C
11
R
7
Ve
F
Z
1
F
Z
2
F
P
2
F
P
3
E/A
Z
f
Z
IN
Frequency
Gain(dB)
H(s) dB
Fb
Comp
H(s) =
1+sR
7
C
12
+C
11
×
(1+sR
8
C
10
)
(1+sR
7
C
11
)
×
[1+sC
10
(R
6
+R
8
)]
×
[ ( )]
1
sR
6
(C
12
+C
11
)
C
12
C
11
Where:
V
IN
= Maximum Input Voltage
V
OSC
= Oscillator Ramp Voltage
Lo = Output Inductor
Co = Total Output Capacitors
F
O
= R
7
×
C
10
×
×
V
IN
V
OSC
1
2
π×
Lo
×
Co
---(15)
C
10
≤
×
2
π ×
Lo
×
F
O
×
Co
R
7
V
OSC
V
IN
C
12
=
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